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LTC4240 CompactPCI Hot Swap Controller with I2C Compatible Interface
FEATURES
s s s
DESCRIPTIO
s s s s s s s s
Allows Safe Board Insertion and Removal from a Live CompactPCITM Bus I2CTM Compatible 2-Wire Interface PRECHARGE Output Biases I/O Pins During Card Insertion and Extraction Controls 3.3V, 5V, 12V and -12V Supplies Foldback Current Limit with Circuit Breaker LOCAL_PCI_RST# Logic On-Board QuickSwitch(R) Enable Output Status LED Driver User Programmable Supply Voltage Power-Up Rate Registers Individual Supply Faults Available in a 28-Pin Narrow SSOP Package
APPLICATIO S
s s
Hot Board Insertion into CompactPCI Bus Electronic Circuit Breaker
, LTC and LT are registered trademarks of Linear Technology Corporation. Hot Swap is a trademark of Linear Technology Corporation. QuickSwitch is a registered trademark of Quality Semiconductor Corp. CompactPCI is a trademark of the PCI Industrial Computer Manufacturers Group. I2C is a trademark of Philips Electronics N.V.
The LTC(R)4240 is a Hot SwapTM controller that allows a board to be safely inserted and removed from a live CompactPCI bus slot. The LTC4240 has a built-in 2-wire I2C compatible interface to allow software control and monitoring of device function and power supply status. Two external N-channel transistors control the 3.3V and 5V supplies, while two internal switches control the -12V and 12V supplies. Electronic circuit breakers protect all four supplies against overcurrent faults. The PWRGD output indicates when all of the supply voltages are within tolerance. The OFF/ON pin is used to cycle the board power or reset the circuit breaker. The I2C interface allows the user to turn the device off or on, set RESETOUT, turn on the status LED driver and ignore 12V, -12V faults. It also allows the user to read the status of the FAULT, RESETIN, RESETOUT, PWRGD, PRSNT1# and PRSNT2# pins. Under a fault condition, the I2C interface can also be used to determine which of the four supplies generated the fault. The LTC4240 is available in a 28-pin narrow SSOP package.
TYPICAL APPLICATIO
CompactPCI BACKPLANE CONNECTOR (MALE) MEDIUM 5V LONG 5V MEDIUM 3.3V LONG 3.3V CompactPCI BACKPLANE CONNECTOR (FEMALE) R22, 2.74
C11 10nF 5VIN 3VIN R21, 1.74 C10 10nF R19 2.55k 1%
Z4
Z3 R1 0.005 Q1 Si7880DP
R2 0.007
C7 0.01F PER PIN
C8 0.01F PER PIN
R3 10
LONG V(I/O)
C9 10nF
R20 1.91k R12 1% 10k R25, 1.2k R28, 200
SCL SDA
3VIN ADDRIN SCL SDA PRSNT2# PRSNT1# 12VIN
3VSENSE GATE
3VOUT
5VIN
5VSENSE
12V -12V 5VIN BD_SEL# Z1 HEALTHY# PCI_RST# R13 10 C4 0.01F GROUND R14 10 C5 0.01F R30 Z2 1k EARLY V(I/O) R17, 1.2k R18 1k
VEEIN OFF/ON FAULT
LTC4240
R29 R15 2k 10
R16 10k C6 0.01F PWRGD RESETIN GND
BE RESETOUT PRECHARGE DRIVE R8, 1k R6 10k 3VOUT
Z1, Z2: SMAJ12CA Z3, Z4: IPMT5.0AT3
R11 18
C3, 4.7nF
R9 24
R7, 12 Q3 MMBT2222A 3VIN
+
U
Q2 Si7880DP
U
U
+
CLOAD (5VOUT)
5VOUT 5V AT 5A
+
R4 10 R5 1k C1 0.047F
3VOUT 3.3V AT 7.6A CLOAD (3VOUT) 5VIN
5VOUT DGND LED 12VOUT
R10 100
+
12VOUT 12V AT 500mA CLOAD (12VOUT) VEEOUT -12V AT 100mA
VEEOUT TIMER C2 0.1F
CLOAD (VEEOUT) TO QUICKSWITCH(R) ENABLE
LOCAL_PCI_RST# TO PCI BRIDGE DEVICE OR EQUIVALENT
4240 TA01
4240f
1
LTC4240
ABSOLUTE
(Notes 1, 2)
AXI U RATI GS
PACKAGE/ORDER I FOR ATIO
TOP VIEW PRSNT1# PRSNT2# 12VIN VEEIN TIMER 5VOUT FAULT PWRGD BE 1 2 3 4 5 6 7 8 9 28 OFF/ON 27 RESETIN 26 12VOUT 25 VEEOUT 24 3VOUT 23 3VSENSE 22 3VIN 21 5VIN 20 5VSENSE 19 GATE 18 PRECHARGE 17 DRIVE 16 DGND 15 LED
Supply Voltages 5VIN .................................................................... -0.3V to 12V 12VIN ................................................................. -0.3V to 14V VEEIN ................................................................... 0.3V to -14V Input Voltages PRSNT1#, PRSNT2#, SCL, RESETIN, OFF/ON .................................................. -0.3V to 12V 5VOUT, 5VSENSE, 3VIN, 3VSENSE, 3VOUT ............................ -0.3V to (5VIN + 0.3V) ADDRIN, PRECHARGE ......................... -0.3V to 5VIN Output Voltages TIMER, FAULT, PWRGD, SDA, RESETOUT, LED, DRIVE, GATE, 12VOUT ....................... -0.3V to 14V VEEOUT ................................................................ -14V to 0.3V BE ............................................. 0.3V to (5VIN + 0.3V) Operating Temperature Range LTC4240C ............................................... 0C to 70C LTC4240I .............................................-40C to 85C Storage Temperature Range .................... 65C to 150C Lead Temperature (Soldering, 10 sec).................. 300C
ORDER PART NUMBER LTC4240CGN LTC4240IGN
GND 10 ADDRIN 11 SDA 12 SCL 13 RESETOUT 14
GN PACKAGE 28-LEAD PLASTIC SSOP
TJMAX = 140C, JA = 135C/W
Consult LTC Marketing for parts specified with wider operating temperature ranges.
The q denotes the specifications which apply over the full operating temperature range, otherwise specifications are at TA = 25C. 12VIN = 12V, VEEIN = -12V, V3VIN = 3.3V, V5VIN = 5V unless otherwise noted.
SYMBOL IDD VLKO PARAMETER V12VIN Supply Current Undervoltage Lockout CONDITIONS OFF/ON = 0V 12VIN 5VIN 3VIN VEEIN VFB = (V5VIN - V5VSENSE), V5VOUT = 0V, TIMER = 0V VFB = (V5VIN - V5VSENSE), V5VOUT = 3V, TIMER = 0V VFB = (V3VIN - V3VSENSE), V3VOUT = 0V, TIMER = 0V VFB = (V3VIN - V3VSENSE), V3VOUT = 2V, TIMER = 0V VTV = (V5VIN - V5VSENSE), V5VOUT = 5V, TIMER = Open VTV = (V5VIN - V5VSENSE), V5VOUT = 0V, TIMER = Open VTV = (V3VIN - V3VSENSE), V3VOUT = 3.3V, TIMER = Open VTV = (V3VIN - V3VSENSE), V3VOUT = 0V, TIMER = Open (V5VIN - V5VSENSE) = 100mV, TIMER = Open (V3VIN - V3VSENSE) = 100mV, TIMER = Open (V5VIN - V5VSENSE) = 200mV, TIMER = Open (V3VIN - V3VSENSE) = 200mV, TIMER = Open OFF/ON = 0V, VGATE = 0V, TIMER = 0V VGATE = 5V, (Note 3) OFF/ON = 0V, VGATE = 2V, TIMER = Open, FAULT = 0V VGATE = (V12VIN - VGATE), IGATE = 1A
q q q q q q q q q q q q q q q q q q q q q
ELECTRICAL CHARACTERISTICS
MIN 7.00 4.10 2.35 15 55 15 55 50 6 50 6 25 25 25 25 - 20 100 2.5
TYP 3 8.00 4.3 2.45 -9 25 70 25 65 55 11 55 11 35 35 35 35 - 65 200 6 600
MAX 8 10.80 4.45 2.55 -10.5 35 85 35 80 60 16 60 16 55 55 55 55 -100 300 8.5 1000
UNITS mA V V V V mV mV mV mV mV mV mV mV s s s s A A mA mV
4240f
VFB
Foldback Current Limit Voltage
VCB
Circuit Breaker Trip Voltage
tOC tSC
Overcurrent Fault Response Time Overcurrent Fault Response Time Short-Circuit Response Time
IGATE(UP) GATE Pin Turn-On Current IGATE(DN) GATE Pin Turn-Off Current IGATE(FAULT) GATE Pin Fault-Off Current VGATE External Gate Voltage
2
U
W
U
U
WW
W
LTC4240
ELECTRICAL CHARACTERISTICS
SYMBOL V12V VVEE ICL ITH TTS VTH PARAMETER 12V Switch Voltage Drop VEE Switch Voltage Drop Current Foldback Current Fault Threshold Thermal Shutdown Temperature Power Good Threshold Voltage
The q denotes the specifications which apply over the full operating temperature range, otherwise specifications are at TA = 25C. 12VIN = 12V, VEEIN = -12V, V3VIN = 3.3V, V5VIN = 5V unless otherwise noted.
CONDITIONS V12V = (V12VIN - V12VOUT), I = 500mA VVEE = (VEEOUT - VEEIN), I = 100mA 12VIN = 12V, 12VOUT = 0V VEEIN = -12V, VEEOUT = 0V 12VIN = 12V VEEIN = -12V Note 4 12VOUT 5VOUT 3VOUT VEEOUT OFF/ON, RESETIN, SCL, SDA, PRSNT1#, PRSNT2# OFF/ON, RESETIN, SCL, SDA, PRSNT1#, PRSNT2# OFF/ON = RESETIN = SDA = SCL = 0V, 5V, PRSNT1#, PRSNT2# = 0V, 5V RESETOUT = FAULT = 12V, OFF/ON = 0V, RESETIN = 3.3V PWRGD = 12V, OFF/ON = 4V 5VSENSE = 5V, 5VOUT = 0V, GATE = 0V 3VSENSE = 3.3V, 3VOUT = 0V, GATE = 0V 5VIN = 5V, TIMER = 0V, OFF/ON = 0V 3VIN = 3.3V, TIMER = Open 3VIN = 3.3V, TIMER = 0V 5VOUT = 5V, OFF/ON = 0V, TIMER = 0V, GATE = 0V 3VOUT = 3.3V, OFF/ON = 0V, TIMER = 0V, GATE = 0V TIMER = 0V, OFF/ON = 0V VPRECHARGE = 1V ADDRIN = 0V, 5V OFF/ON = 0V, TIMER = 0V TIMER = 5V, OFF/ON = 2V
q q q q q q q q q q q q q q q q q q q q q q q q q q q q q q q q q
MIN
TYP 300 125
MAX 600 250 - 800 350
UNITS mV mV mA mA mA mA C V V V V V V A A A A A A mA A A A A A A A A mA V V V V V V kHz s s s
4240f
- 50 50 -550 225 10.8 4.50 2.8 - 10 2
-350 250
- 1250 - 1900 500 800 150 11.1 4.65 2.9 - 10.5 11.4 4.75 3.0 - 10.8 0.8 0.08 0.08 0.08 0.08 55 55 0.8 250 250 237 120 -950 2 2 2 2 100 100 1.5 600 500 400 200 -1200 10 0.1
VIL VIH IIN
Input Low Voltage Input High Voltage Input Current PRSNT1#, PRSNT2#, OFF/ON, RESETIN, SDA, SCL RESETOUT, FAULT Leakage Current PWRGD Leakage Current 5VSENSE Input Current 3VSENSE Input Current 5VIN Input Current 3VIN Input Current 5VOUT Input Current 3VOUT Input Current VEEIN Input Current Precharge Input Current ADDRIN
ITIMER VTIMER RDIS
TIMER Pin Current TIMER Threshold Voltages 12VOUT Discharge Impedance 5VOUT Discharge Impedance 3VOUT Discharge Impedance VEEOUT Discharge Impedance CMOS Output High Voltage CMOS Output Low Voltage Output Low Voltage Output Low Voltage PRECHARGE Reference Voltage SCL Clock Frequency Start Condition Setup Time Bus Free Time Between Stop and Start Start Condition Hold Time
-6 15 5
- 11.5 28 5.5 430 50 150 650
-17 55 6.5 1000 100 300 1000 0.4 0.4 0.8
VOH VOL
BE, I = -100A BE, I = 100A PWRGD, RESETOUT, FAULT, SDA(I = 3mA) LED (I = 10mA) V5VIN = 5V
q 5VIN - 0.4 q q q q
VPXG fSCL tSUSTA tBUF tHDSTA
0.9
1
1.1 100
I2C Timing (Note 4) 4.7 4.7 4
3
LTC4240
The q denotes the specifications which apply over the full operating temperature range, otherwise specifications are at TA = 25C. 12VIN = 12V, VEEIN = -12V, V3VIN = 3.3V, V5VIN = 5V unless otherwise noted.
SYMBOL tSUSTP tHDDAT tSUDAT tLOW tHIGH tf tr PARAMETER Stop Condition Setup Time Data Hold Time Data Setup Time Clock Low Period Clock High Period Clock/Data Fall Time Clock/Data Rise Time Note 3: OFF/ON pin pulled up to 5V by 1.2k resistor. Note 4: Parameters guaranteed by design and not tested. CONDITIONS MIN 4 300 250 4.7 4.0 300 1000 TYP MAX UNITS s ns ns s s ns ns
ELECTRICAL CHARACTERISTICS
Note 1: Absolute Maximum Ratings are those values beyond which the life of a device may be impaired. Note 2: All currents into device pins are positive; all currents out of device pins are negative. All voltages are referenced to ground unless otherwise specified.
TYPICAL PERFOR A CE CHARACTERISTICS
Gate Pin Fault Current vs Temperature
8 VGATE = 2V FAULT = 0V 350
GATE PIN FAULT CURRENT (mA)
GATE PIN CURRENT (A)
6
GATE PIN CURRENT (A)
4
2
0 -50
-25
0 25 50 TEMPERATURE (C)
12VIN Supply Current vs Temperature
4.0 OFF/ON = 0V 280
12VIN SUPPLY CURRENT (mA)
3.6
260
5VIN SUPPLY CURRENT (mA)
3VIN SUPPLY CURRENT (A)
3.2
2.8
2.4 -50
-25
0 25 50 TEMPERATURE (C)
4
UW
75 100
4240 G01
Gate Pin Turn-Off Current vs Temperature
VGATE = 5V OFF/ON = 2V -20
Gate Pin Turn-On Current vs Temperature
VGATE = 0V OFF/ON = 0V
300 -40
250
-60
200
150
-80
100 -50
-25
0 25 50 TEMPERATURE (C)
75
100
4240 G02
-100 -50
-25
0 25 50 TEMPERATURE (C)
75
100
4240 G03
3VIN Supply Current vs Temperature
OFF/ON = 0V 1.0
5VIN Supply Current vs Temperature
OFF/ON = 0V
0.9
0.8
0.7
240
0.6
75
100
4240 G04
220 -50
-25
0 25 50 TEMPERATURE (C)
75
100
4240 G05
0.5 -50
-25
0 25 50 TEMPERATURE (C)
75
100
4240 G06
4240f
LTC4240 TYPICAL PERFOR A CE CHARACTERISTICS
VEEIN Supply Current vs Temperature
-0.8 OFF/ON = 0V
12VIN FOLDBACK CURRENT LIMIT (A) VEEIN SUPPLY CURRENT (mA)
12VOUT = 10V 1.2
VEE FOLDBACK CURRENT LIMIT (A)
-0.9
-1.0
-1.1
-1.2 -50
-25
0 25 50 TEMPERATURE (C)
12V Output Current
1.6 0.5 12VIN = 12V TA = 25C 0.4
OUTPUT CURRENT (A) OUTPUT CURRENT (A)
1.2
0.3
0.8
0.2
0.4
0.1
0 0 2 4 6 8 OUTPUT VOLTAGE (V) 10 12
4240 G10
0 0 -2 -4 -6 -8 OUTPUT VOLTAGE (V) -10 -12
4240 G11
12VOUT PWRGD THRESHOLD VOLTAGE (V)
3VOUT PWRGD Threshold Voltage vs Temperature
3.00
3VOUT PWRGD THRESHOLD VOLTAGE (V) 5VOUT PWRGD THRESHOLD VOLTAGE (V)
VEEOUT PWRGD THRESHOLD VOLTAGE (V)
2.95
2.90
2.85
2.80 -50
-25
0 25 50 TEMPERATURE (C)
UW
75
4240 G07
12VIN Foldback Current Limit vs Temperature
1.6 0.7 0.6 0.5 0.4 0.3
VEEIN Foldback Current Limit vs Temperature
VEEOUT = -10V
0.8
VEEOUT = 0V 0.2 0.1 0 -50
0.4
12VOUT = 0V
100
0 -50
-25
0 25 50 TEMPERATURE (C)
75
100
4240 G08
-25
0 25 50 TEMPERATURE (C)
75
100
4240 G09
-12V Output Current
VEEIN = -12V TA = 25C 11.4 11.3 11.2 11.1 11.0 10.9
12VOUT PWRGD Threshold Voltage vs Temperature
10.8 -50
-25
0 25 50 TEMPERATURE (C)
75
100
4240 G12
5VOUT PWRGD Threshold Voltage vs Temperature
4.75 -10.2 -10.3 -10.4 -10.5 -10.6 -10.7
VEEOUT PWRGD Threshold Voltage vs Temperature
4.70
4.65
4.60
4.55
75
100
4240 G13
4.50 -50
-25
0 25 50 TEMPERATURE (C)
75
100
4240 G14
-10.8 -50
-25
0 25 50 TEMPERATURE (C)
75
100
4240 G15
4240f
5
LTC4240 TYPICAL PERFOR A CE CHARACTERISTICS
3VSENSE Input Current vs Temperature
65 3VSENSE = 3.3V
3VSENSE INPUT CURRENT (A) 5VSENSE INPUT CURRENT (A)
60
60
TIMER PIN CURRENT (mA)
55
50
45 -50
-25
0 25 50 TEMPERATURE (C)
Timer Pin Turn-On Current vs Temperature
-10.0 -10.5
TIMER PIN CURRENT (A) TIMER THRESHOLD VOLTAGE (V)
CIRCUIT BREAKER RESPONSE TIME (s)
OFF/ON = 0V VTIMER = 0V
-11.0 -11.5 -12.0 -12.5 -13.0 -50
-25
0 25 50 TEMPERATURE (C)
12VIN UVLO Threshold Voltage vs Temperature
9.0
12VIN UVLO THRESHOLD VOLTAGE (V) 3VIN UVLO THRESHOLD VOLTAGE (V)
8.5
2.50
8.0
2.45
7.5
2.40
7.0 -50
-25
0 25 50 TEMPERATURE (C)
75
100
4240 G22
2.35 -50
-25
0 25 50 TEMPERATURE (C)
75
100
4240 G23
5VIN UVLO THRESHOLD VOLTAGE (V)
6
UW
75 100
4240 G16
5VSENSE Input Current vs Temperature
65 5VSENSE = 5V 34 32 30 28 26 24 22 20 45 -50 -25 0 25 50 TEMPERATURE (C) 75 100
4240 G17
Timer Pin Turn-Off Current vs Temperature
OFF/ON = 2V VTIMER = 5V
55
50
18 -50
-25
0 25 50 TEMPERATURE (C)
75
100
4240 G18
Timer Threshold Voltage vs Temperature
6.0 40
5V/3.3V Circuit Breaker Overcurrent Fault Response Time vs Temperature
TIMER PIN FLOATING VIN - VSENSE = 0.1V 38
5.8
5.6
36
5.4
34
5.2
32
75
100
4240 G19
5.0 -50
-25
0 25 50 TEMPERATURE (C)
75
100
4240 G20
30 -50
-25
0 25 50 TEMPERATURE (C)
75
100
4240 G21
3VIN UVLO Threshold Voltage vs Temperature
2.55 4.45
5VIN UVLO Threshold Voltage vs Temperature
4.40
4.35
4.30
4.25 -50
-25
0 25 50 TEMPERATURE (C)
75
100
4240 G24
4240f
LTC4240 TYPICAL PERFOR A CE CHARACTERISTICS
VEEIN UVLO Threshold Voltage vs Temperature
12V INTERNAL SWITCH VOLTAGE DROP (mV)
VEEIN UVLO THRESHOLD VOLTAGE (V)
I = 500mA 450 400 350 300 250 200 150 -50
VEE INTERNAL SWITCH VOLTAGE DROP (mV)
-7.6 -8.0 -8.4 -8.8 -9.2 -9.6
-10.0 -50
-25
0 25 50 TEMPERATURE (C)
3V Foldback Current Limit Voltage vs Temperature
3V FOLDBACK CURRENT LIMIT VOLTAGE (mV)
3VOUT = 2V 60
5V FOLDBACK CURRENT LIMIT VOLTAGE (mV)
80
3V CIRCUIT BREAKER TRIP VOLTAGE (mV)
40 3VOUT = 0V 20
VTIMER = 0V 0 -50 -25 0 25 50 TEMPERATURE (C)
5V Circuit Breaker Trip Voltage vs Temperature
80
5V CIRCUIT BREAKER TRIP VOLTAGE (mV)
3VOUT INPUT CURRENT (A)
60 5VOUT = 5V 40
140
5VOUT INPUT CURRENT (A)
20
5VOUT = 0V
VTIMER = OPEN 0 -50 -25 0 25 50 TEMPERATURE (C)
UW
75 100
4240 G25
12VIN Internal Switch Voltage Drop vs Temperature
500 200
VEEIN Internal Switch Voltage Drop vs Temperature
I = 100mA
160
120
80
-25
0 25 50 TEMPERATURE (C)
75
100
4240 G26
40 -50
-25
0 25 50 TEMPERATURE (C)
75
100
4240 G27
3V Circuit Breaker Trip Voltage vs Temperature
80 100
5V Foldback Current Limit Voltage vs Temperature
60 3VOUT = 3.3V 40
80 5VOUT = 3V 60
40 5VOUT = 0V VTIMER = 0V 0 -50 -25 0 25 50 TEMPERATURE (C) 75 100
4240 G31
20
3VOUT = 0V
20
75
100
4240 G28
VTIMER = OPEN 0 -50 -25 0 25 50 TEMPERATURE (C)
75
100
4240 G29
3VOUT Input Current vs Temperature
160 3VOUT = 3.3V OFF/ON = 0V 280 300
5VOUT Input Current vs Temperature
5VOUT = 5V OFF/ON = 0V
260
120
240
100
220
75
100
4240 G32
80 -50
-25
0 25 50 TEMPERATURE (C)
75
100
4240 G33
200 -50
-25
0 25 50 TEMPERATURE (C)
75
100
4240 G34
4240f
7
LTC4240
PI FU CTIO S
PRSNT1# (Pin 1): PCI Present Detect Input 1. PRSNT1# and PRSNT2# are readable over the I2C Bus. PRSNT1# and PRSNT2# indicate the maximum power used by the card. Do not float. PRSNT2# (Pin 2): PCI Present Detect Input 2. Do not float. 12VIN (Pin 3): 12V Supply Input. A 0.5 switch is internally connected between 12VIN and 12VOUT with foldback current limit. An undervoltage lockout circuit prevents the switches from turning on while the 12VIN pin is below 8V. 12VIN provides power to some of the LTC4240's internal circuitry. See Input Transient Protection section on how to protect 12VIN from large voltage transients. VEEIN (Pin 4): -12V Supply Input. A 1 internal switch is connected between VEEIN and VEEOUT with foldback current limit. An undervoltage lockout circuit prevents the switches from turning on while VEEIN is above - 9V. See Connecting VEEIN section for more notes on VEEIN and VEEOUT. Also refer to Input Transient Protection section. TIMER/AUX 12VIN (Pin 5): Current Fault Inhibit Timing Input. Connect a capacitor from TIMER to GND. With the LTC4240 turned off (OFF/ON = HIGH), the TIMER pin is internally held at GND. When the device is turned on, an 11.5A pull-up current source is connected to TIMER. Current limit faults will be ignored until the voltage at the TIMER pin rises above 5.5V. The Timer capacitor also serves as an auxiliary charge reservoir for internal VCC in the event the 12VIN pin voltage glitches below the LTC4240 UVL threshold voltage. 5VOUT (Pin 6): 5V Output Sense. The PWRGD pin will not pull low until the 5VOUT pin voltage exceeds 4.65V. When the power switches are turned off, a 50 resistor pulls 5VOUT to ground. FAULT (Pin 7): Open-Drain Fault Output . FAULT is pulled low when a current limit fault is detected. Current limit faults are ignored until the voltage at the TIMER pin is above 5.5V. Once the TIMER cycle is complete, FAULT pulls low and the LTC4240 turns off (in the event of an overcurrent fault lasting longer than 35s). The LTC4240 will remain in the off state until the OFF/ON pin is cycled high then low or power is cycled. Note that the OFF/ON cycling can also be performed using I2C bus. PWRGD (Pin 8): Open-Drain Power Good Output. Connect the CPCI HEALTHY# signal to the PWRGD pin. PWRGD remains low while V12VOUT 11.1V, V3VOUT 2.9V, V5VOUT 4.65V and VEEOUT -10.5V. When any of the supplies drops below its power good threshold voltage, PWRGD will go high after a 10s deglitching time. The switches will not be turned off when PWRGD goes high, unless a fault has occurred. The CPCI specification calls for a 0.01F bypass capacitor on the backplane for HEALTHY#. BE (Pin 9): QuickSwitch Bus Enable Output. The BE output remains high until power is good on all supplies. This serves to isolate the I/O data lines during live insertion. This is a CMOS output powered by 5VIN. GND (Pin 10): Analog Ground. Connect to analog ground plane. ADDRIN (Pin 11): I2C Address Programming Input. The I2C address is programmed by connecting the ADDRIN pin to a resistor divider between the 5VIN pin and GND. See Table 1 for 1% resistor values and corresponding addresses. Resistors must be placed close to the ADDRIN pin to minimize errors due to stray capacitance and resistance on the board trace. Connect this pin to ground if I2C is not used. SDA (Pin 12): I2C Data Input and Output. Note that TTL levels are used. Connect this pin to ground if I2C is not used. SCL (Pin 13): I2C Clock Input, 100kHz Maximum. Note that TTL levels are used. Do not float. Connect this pin to ground if I2C is not used. RESETOUT (Pin 14): Open-Drain Reset Output. Connect the CPCI LOCAL_PCI_RST# signal to the RESETOUT pin. RESETOUT is the logical combination of RESETIN, PWRGD, and I2C RESETOUT latch output. LED (Pin 15): CPCI Status LED. Pulls low to light LED when RESETOUT is low or when the I2C LED latch is set. DGND (Pin 16): Digital Ground. Connect to ground plane. DRIVE (Pin 17): External transistor's base drive output for bus precharge. Connects to the base of an external NPN emitter-follower which in turn biases the PRECHARGE
4240f
8
U
U
U
LTC4240
PI FU CTIO S
node. An external 1k resistor between the transistor's base and 3VIN is needed. PRECHARGE (Pin 18): Precharge Monitor Input. An internal error amplifier servos the DRIVE pin voltage to keep the precharge node at 1V. Becomes valid when long 5V and 3.3V power pins make contact .Tie pins 17 and 18 together if precharge function is unused. GATE (Pin 19): High Side Gate Drive for the External 3.3V and 5V N-Channel Power Transistors. An external series RC network is required for the current limit loop compensation and to set the maximum ramp-up rate. During power-up, the slope of the voltage rise at the GATE pin is set by the 65A current source charging the external GATE capacitor or by the 3.3V or 5V current limit and the associated output capacitor. During power-down, a 200A current source pulls the GATE pin to GND. The voltage at the GATE pin will be modulated to maintain a constant current when either the 3.3V or 5V supply goes into current limit and the TIMER pin is less than 5.5V. Once the TIMER pin is above 5.5V, and in the event of a current fault condition lasting for longer than 35s, the GATE pin is immediately pulled to GND. 5VSENSE (Pin 20): 5V Current Limit Sense. A sense resistor placed between 5VIN and 5VSENSE determines the current limit for this supply. A foldback current feature makes the current limit decrease as the voltage at the 5VOUT pin approaches 0V. To disable the current limit, 5VSENSE and 5VIN must be tied together. 5VIN (Pin 21): 5V Supply Sense Input. An undervoltage lockout circuit prevents the switches from turning on when the voltage at the 5VIN pin is less than 4.3V. At least one long pin must be connected to 5VIN to ensure precharge output. See Input Transient Protection section. 3VIN (Pin 22): 3.3V Supply Sense Input. An undervoltage lockout circuit prevents the switches from turning on when the voltage at the 3VIN pin is less than 2.45V. If no 3.3V input supply is available, connect two series diodes between 5VIN and 3VIN (tie anode of first diode to 5VIN and cathode of second diode to 3VIN, Figure 15). At least one long pin must be connected to 3VIN to ensure precharge output. See Input Transient Protection section. 3VSENSE (Pin 23): 3.3V Current Limit Sense. A sense resistor placed between 3VIN and 3VSENSE determines the current limit for this supply. A foldback feature makes the current limit decrease as the voltage at the 3VOUT pin approaches 0V. To disable current limit, 3VSENSE and 3VIN must be tied together. 3VOUT (Pin 24): 3.3V Output Sense. The PWRGD pin cannot pull low until the 3VOUT pin voltage exceeds 2.9V. If no 3.3V input supply is available, tie the 3VOUT pin to the 5VOUT pin. When the power switches are turned off, a 150 resistor pulls 3VOUT to ground. VEEOUT (Pin 25): -12V Supply Output. An internal 1 switch is connected between VEEIN and VEEOUT. VEEOUT must exceed -10.5V before the PWRGD pin pulls low. When the power switches are turned off, a 650 resistor pulls VEEOUT to ground. 12VOUT (Pin 26): 12V Supply Output. A 0.5 switch is connected between 12VIN and 12VOUT. 12VOUT must exceed 11.1V before the PWRGD pin can pull low. When the power switches are turned off, a 430 resistor pulls 12VOUT to ground. RESETIN (Pin 27): PCI Reset Input. Connect the CPCI PCI_RST# signal to the RESETIN pin. Pulling RESETIN low will cause RESETOUT to pull low. Note that the I2C RESETIN latch output can also set RESETOUT. Do not float. OFF/ON (Pin 28): OFF/ON Input. Connect the CPCI BD_SEL# signal to the OFF/ON pin. When the OFF/ON pin is pulled low, the GATE pin is pulled high by a 65A current source and the internal 12V and -12V switches are turned on. When the OFF/ON pin is pulled high, the GATE pin will be pulled to ground by a 200A current source and the 12V and -12V switches turn off. Cycling the OFF/ON pin high and low will reset a tripped circuit breaker and start a new power-up sequence. The I2C OFF/ON latch output can also be used to reset the electronic circuit breaker. Do not float.
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LTC4240
BLOCK DIAGRA
5VIN 21 5VSENSE 20 5VOUT 70mV, TIMER LO 165mV, TIMER HI
+-
+
A1
+- +
55mV CP1
-
CP2
55mV
CP3
+-
VCB 4.3V UVL OFF/ON 28
-
-
VCB
-+
2.45V UVL Q4
FAULT 7 Q13
PWRGD 8 Q12
LOGIC 16 9 BE DGND
RESETIN 27 Q5 8V UVL Q11 12VIN Q10 11.5A Q8 1.2V Q6
+
CP6 Q9 Q7
+
CP5
-
1.2V 3 12VIN 26 12VOUT 5 TIMER -9V UVL 4 VEEIN 25 VEEOUT
-
10 GND
DRIVE
10
+
-
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GATE 19 12Vin 65A A2 Q1 200A 3VOUT 3VSENSE 23 3VIN 22 3VOUT 24 5VOUT 6
+ -
-+
65mV, TIMER LO 165mV, TIMER HI
Q2
Q3
-+ +
1.2V
1.2V
+
CP4
-
12 SDA
13 SCL 11 ADDRIN 2 PRSNT2# 1 PRSNT1#
15 LED
14 RESETOUT
Q14 A3
- +
1V
17
18 PRECHARGE
4240 BD
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LTC4240
APPLICATIO S I FOR ATIO
The LTC4240 is a Hot Swap controller that allows a board to be safely inserted and removed from a CompactPCI bus slot. The LTC4240 has built-in 2-wire I2C compatible interface hardware to allow software control and monitoring of device function and power supply status. Hot Circuit Insertion When a circuit board is inserted into a live CompactPCI (CPCI) backplane slot, supply bypass capacitors on the board can draw huge supply transient currents from the CPCI backplane power bus. The transient currents can cause glitches on the power bus, thus causing other boards in the system to reset. The LTC4240 is designed to turn a board's supply voltages on and off in a controlled manner, allowing the board to be safely inserted or removed from a live CPCI slot without disturbing the system power supplies. The device also protects the supplies from shorts, precharges the bus I/O pins during insertion and extraction and monitors the supply voltages. The LTC4240 includes an I2C compatible interface, which allows software control of device functions. The LTC4240 is specifically designed for CPCI applications where it resides on the plug-in board. For best results, a well bypassed backplane is recommended. LTC4240 Feature Summary * Allows safe board insertion and removal from a CPCI backplane. Status LED visually identifies when a board is ready for removal. * Controls all four CPCI supplies: -12V, 12V, 3.3V and 5V. * Foldback current limit: An analog current limit with a value that depends on the output voltage. If the output is shorted to ground, the current limit drops to keep power dissipation and supply glitches to a minimum. * 12V and -12V circuit breakers: if either supply remains in current limit for more than 35s, the circuit breaker will trip, the supplies will turn off and the FAULT pin pulls low.
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* Adjustable 5V and 3.3V circuit breakers: if either supply exceeds current limit for more than 35s, the circuit breaker will trip, the supplies will be turned off and the FAULT pin will be pulled low. In addition, an analog loop will servo the GATE pin to limit the current to three times circuit breaker limit during transient conditions. * I2C interface: software control allows user to both write to and read from the device. The user can turn the device off and on, set the status LED, set RESETOUT and disable faults on 12VIN and VEEIN. The user can also read the device status: FAULT, RESETIN, RESETOUT PWRGD, PRSNT1#, PRSNT2#, FAULTCODE0 and FAULTCODE1. If a fault occurs, the FAULTCODE bits identify which supply generated the fault. * Current limit during power-up: the supplies are allowed to power-up in current limit. This allows the LTC4240 to power-up boards with widely varying capacitive loads without tripping the circuit breaker. The maximum allowable power-up time is programmable using an external capacitor connected to the TIMER pin. See TIMER section * Internal 12V and -12V power switches. * PWRGD output: indicates the voltage status of the four supply voltages. * PCI_RST# is combined with HEALTHY# and with the I 2 C RESETIN latch output to create LOCAL_PCI_RST# output. If HEALTHY# asserts, LOCAL_PCI_RST# is asserted independent of the other two inputs. * Precharge output: an internal reference and amplifier provide 1V for biasing bus I/O connector pins during CPCI card insertion and extraction. * Space saving 28-pin SSOP package. I2C Interface The LTC4240 incorporates an I2C compatible 2-wire (clock and data) interface that allows the user to easily query and control the status of the LTC4240. A single analog input pin selects 1 of 32 allowed addresses. The I2C bus can be
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LTC4240
APPLICATIO S I FOR ATIO
used to turn off/on the power switches, turn on the status LED (alerting the user that its safe to remove the plug-in board), and assert the LOCAL_PCI_RST# signal. The I2C bus is also used to read the logic signals of several device pins: FAULT, PWRGD, RESETIN, and RESETOUT. Additionally, when a supply generates a current fault, the I2C bus can be used to determine which supply generated the fault. See Send Byte and Receive Byte sections for a full description of all I2C features. The LTC4240 supports Send Byte and Receive Byte protocols. Communication is achieved using the SCL and SDA pins (TTL compatible input thresholds). The SCL pin is the clock input from the I2C bus (host) to the LTC4240 (slave). The maximum SCL frequency is 100kHz. SDA is the bidirectional data transfer line between the I2C bus and the LTC4240. Send Byte and Receive Byte protocols are both comprised of 2 bytes. The first byte for both is the address byte. All communication begins with a START command. Programming the I2C Address The voltage on the ADDRIN pin determines the I2C address. The ADDRIN voltage is set externally with a resistor divider from 5VIN to ground (resistor placement must be close to the pin, do not place a bypass capacitor on ADDRIN). This voltage is fed to a 5-bit A/D and compared against the address byte clocked in by the I2C bus. The 5bit A/D allows 32 unique LTC4240 devices to be connected on the same I2C bus. 1% resistors should be used to place the voltage at ADDRIN approximately 0.5 LSB away from each code transition. Table 1 shows recommended resistor values for each of the address code segments. The resistor ratio for each code segment has been optimized for best performance over the specified temperature range. The parallel resistance for the address setting resistors should be kept under 10k.
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Table 1. Suggested ADDRIN 1% Resistor Values
ADDR RECOMMENDED ALLOWED ADDRIN R19(TOP) R20(BOT) CODE ADDRIN VOLTAGE VOLTAGE RANGE RESISTOR RESISTOR 00 01 02 03 04 05 06 07 08 09 10 11 12 13 14 15 16 17 18 19 20 21 22 23 24 25 26 27 28 29 30 31 0.108125 0.264375 0.420625 0.576875 0.733125 0.889375 1.045625 1.201875 1.358125 1.514375 1.670625 1.826875 1.983125 2.139375 2.295625 2.451875 2.608125 2.764375 2.920625 3.076875 3.233125 3.389375 3.545625 3.701875 3.858125 4.014375 4.170625 4.326875 4.483125 4.639375 4.795625 4.951875 0.080 to 0.136 0.236 to 0.293 0.393 to 0.449 0.549 to 0.605 0.705 to 0.761 0.861 to 0.918 1.018 to 1.074 1.174 to 1.230 1.330 to 1.386 1.486 to 1.543 1.643 to 1.699 1.799 to 1.860 1.955 to 2.021 2.111 to 2.175 2.268 to 2.330 2.424 to 2.488 2.580 to 2.644 2.736 to 2.800 2.888 to 2.950 3.044 to 3.110 3.200 to 3.262 3.356 to 3.421 3.513 to 3.574 3.669 to 3.731 3.825 to 3.886 3.981 to 4.041 4.138 to 4.190 4.294 to 4.349 4.450 to 4.499 4.606 to 4.651 4.763 to 4.805 4.919 to 4.962 8660 2550 2550 2550 2550 2550 3830 2550 2550 1150 1020 8660 2550 2550 1130 1370 2550 2550 2550 715 1150 1150 1150 357 2550 249 1070 178 133 102 105 100 191 140 237 332 442 549 1020 806 953 499 511 4990 1690 1910 1130 1330 2800 3160 3570 1150 2100 2430 2800 1020 8660 1020 5360 1150 1150 1300 2430 10000
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LTC4240
APPLICATIO S I FOR ATIO
START and STOP Commands The START command is defined as a high to low transition of the SDA line while the SCL line is high. It is an asynchronous event issued by the host, waking up all slave devices and alerting them that a slave address is being written onto the bus. Only the slave device that matches the address will communicate with the host. The STOP command is defined as a low to high transition on the SDA line while SCL is high. It is also an asynchronous event issued by the host to signal the termination of the data transfer. Other than START and STOP commands, the SDA line is allowed to change states only when SCL is low. Address Byte Once the LTC4240 has detected a START command, it clocks in the SDA line on the succeeding 9 SCL rising edges. The first 7 bits clocked in contain the address of the slave device targeted by the host. The first (MSB) address bit must be set to low and the second bit must be set to high. The next 5 bits are fed into a digital comparator and compared against the output of an internal 5-bit A/D. If the comparison is true, then there is an address match and the LTC4240 continues to communicate with the host device. The LTC4240 proceeds to acknowledge the address match by pulling the SDA line low while SCL is low, just before the 9th SCL rising edge. Figures 1 and 3 show a timing diagram of the START condition and address byte for both the Send Byte and Receive Byte protocols. Note that the SDA bit clocked in with the 8th SCL edge determines whether the host is sending or receiving information to/ from the LTC4240. Send Byte Protocol The Send Byte protocol allows a host to write information into the LTC4240 and command the LTC4240 to perform certain predetermined functions. The host initiates communication with a START bit followed by 7 address bits. The address bits are followed by the R/W bit, which is low for Send Byte. The 9th bit is asserted low by the LTC4240
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to acknowledge when there has been an address match. The only time the LTC4240 writes data onto the SDA bus during a send byte is to acknowledge the address and command bytes. The first 8 bits are referred to collectively as the address byte. The command byte follows the address byte. The command byte contains the information sent from the host to the LTC4240. After the LTC4240 acknowledges the address byte, each of the next 8 SCL rising edges shifts SDA from the host into a shift register inside the LTC4240. The first 2 bits clocked into the shift register (2 MSBs of the command latch) are not used by the LTC4240. Only the 6 LSBs are stored in the command latch on the falling edge of the 8th clock during the command byte. The output of the command latch remains fixed until the next Send Byte command overwrites it. Note that if power is turned off (5VIN < 2V), the command and data latches will be cleared. Figure 1 shows the timing diagram of the entire send byte protocol. Transmission ends when the host issues a STOP command. Table 2 defines the functions of the 6 command bits. Note that some of these functions can override, or can be overridden by, other circuitry and pins of the LTC4240. Figure 2 shows the relationship between bits C1 to C3 and other LTC4240 signals. Receive Byte Protocol The Receive Byte protocol is used by the host to read data from the LTC4240 data latch. This protocol begins with a START command, issued by the host, followed by 7 address bits. The address bits are followed by the R/W bit, which is high for Receive Byte. The 9th bit is used by the LTC4240 to acknowledge when there is an address match. The data byte then follows the address byte. This byte contains LTC4240 status information. After the LTC4240 acknowledges the address byte, it shifts 8 bits of data onto the SDA line. Figure 3 shows the entire Receive Byte timing diagram. Note that neither the host or the slave acknowledges the data byte (SDA line stays high during 9th clock edge of the data byte).
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LTC4240
APPLICATIO S I FOR ATIO
ADDRESS BYTE
SCL 1 2 3 4 5 6
7
START SDA 0 1 ADDR 4 ADDR 3 ADDR 2 ADDR 1 ADDR 0 R/WR=0 ACK XX XX C5 C4 C3 C2 C1 XX ACK
Table 2. Command Byte Definitions
HIGH C7 C6 C5 C4 C3 C2 C1 C0 Don't care Don't care Ignore VEEOUT faults Ignore 12VOUT faults Sets RESETOUT Turns OFF/ON to OFF Overrides OFF/ON pin Turns on LED open drain Don't care LOW Don't care Don't care Don't ignore VEEOUT faults Don't ignore 12VOUT faults Does not set RESETOUT low Does not set OFF/ON Does not override OFF/ON pin Does not turn on LED open drain Don't care POWER-UP STATE N/A N/A LOW LOW LOW LOW LOW N/A
LED
C1 RESETOUT C1 TURNS ON THE EXTERNAL STATUS LED INDEPENDENT OF RESETOUT.
Figure 2. Send Byte Command Latch and Logic
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COMMAND BYTE
8 9 1 2 3 4 5 6 7
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LATCH COMMAND BYTE
8 9
STOP
4240 F01
Figure 1. Send Byte Protocol
GATE
RESETOUT
C2 OFF/ON
C3 RESETIN PWRGD
C2 PULLS DOWN THE GATE OF THE EXTERNAL N-CHANNEL SWITCHES. IT ALSO TURNS OFF THE 12VIN AND VEEIN INTERNAL POWER SWITCHES.
C3 IS USED TO SET LOCAL_PCI_RST# (RESETOUT).
4240 F02
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LTC4240
APPLICATIO S I FOR ATIO
Table 3 shows the definition for each data bit. PWRGD, FAULT, RESETIN, and RESETOUT external pins can be monitored. PRSNT1# and PRSNT2# are PCI signals that provide information on the power requirements of the board. Refer to PCI local bus specifications for a detailed description. FAULTCODE1 and FAULTCODE0 are two internal binary encoded signals that, along with FAULT, indicate which of the four supplies generated a fault. Note that the FAULTCODE signals are valid only when FAULT has been asserted low. See Table 4 for description. Status LED The main function of the LED is to alert the user when it is permissible to physically extract the board. The LED output of the LTC4240 is an open drain N-channel device capable of sinking 10mA from an externally connected LED. This LED lights up when RESETOUT (LOCAL_PCI_RST#) is asserted. Upon application of Early Power, the long 5V pins will power up the LTC4240 and light up the Status LED. It will remain on until PWRGD (HEALTHY#) is asserted and RESETIN (PCI_RST#) is deasserted, and the board enters normal operation. Note that this LED can also be turned on via the I2C 2-wire interface. CPCI Connection Pin Sequence The staggered length of the CPCI male connector pins ensures that all power supplies are physically connected
Table 3. STATUS Byte Definitions
S7 S6 S5 S4 S3 S2 S1 S0 Logic state of the PRSNT2# pin Logic state of the PRSNT1# pin Logic state of the PWRGD pin Logic state of the RESETOUT pin Logic state of the RESETIN pin FAULTCODE1 (see Table 4) FAULTCODE0 (see Table 4) Logic state of the FAULT pin
ADDRESS BYTE
SCL 1 2 3 4 5 6 7 8 9
START SDA 0 1 ADDR 4 ADDR 3 ADDR 2 ADDR 1 ADDR 0 R/WR=1 ACK S7 S6 S5 S4 S3 S2 S1 S0 ACK
Figure 3. Receive Byte Protocol
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to the LTC4240 before back-end power is allowed to ramp (BD_SEL# asserted low). The long pins, which include 5V, 3.3V, V(I/O) and GND mate first. The short pins, which includes BD_SEL# (OFF/ON), mate last. At least one long 5V power pin must be connected to the LTC4240 in order for the PRECHARGE voltage to be available during Early Power. The external components connected to the precharge pin require long 3.3V. The following is a typical hot plug sequence: 1. ESD clips make contact. 2. Long power and ground pins make contact and Early Power is established (see Early Power section). The 1V PRECHARGE voltage becomes valid at this stage. Power is applied to the pull-up resistors connected to FAULT, PWRGD and OFF/ON pins. The status LED is lit, indicating that the plug-in board is in the process of being connected (LOCAL_PCI_RST# is asserted). All power switches are off. 3. Medium length pins make contact. There are six 5V and eight 3.3V medium length power pins, bringing the 5V total to 8 pins and the 3.3V total to 10 pins. The maximum DC current for the 3.3V and 5V supplies is 10A and 8A, respectively. The I2C command latch is initialized to allow seamless CPCI Hot Swap operation. The LTC4240 can be used as a Hot Swap controller without ever establishing I2C communication. Both FAULT and PWRGD continue to be pulled up high at this
Table 4. FAULTCODE Encoding Description for Receive Byte
FAULTCODE0 LO LO HI HI X FAULTCODE1 LO HI LO HI X
DATA BYTE
1 2 3 4 5 6 7 8 9
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FAULT LO LO LO LO HI
Supply Causing Fault 3VIN 5VIN 12VIN VEEIN None
STOP
4240 F03
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LTC4240
APPLICATIO S I FOR ATIO
stage in the hot plug sequence, indicating that the LTC4240 is in reset mode with all power switches off (BD_SEL# is still pulled high to long 5V). The 12V and -12V supplies make contact at this stage. Zener clamps Z1 and Z2 plus shunt RC snubbers R13C4 and R14-C5 help protect the 12VIN and VEEIN pins, respectively, from large transient voltages during hot insertion and short-circuit conditions. The signal pins also connect at this point. This includes the HEALTHY# signal connecting to the PWRGD pin and the PCI_RST# signal connecting to the RESETIN pin. The PWRGD and RESETIN signals are combined internally with Bit 3 (C3) of the I2C command latch (see Send Byte protocol) to generate the LOCAL_PCI_RST# signal, which is available at the RESETOUT pin. 4. Short pins make contact. BD_SEL# signal connects to the OFF/ON pin. This starts the electrical part of the connection process. If the BD_SEL# signal is grounded on the backplane, then the electrical connection process starts immediately. Note that the electrical connection process can be interrupted with the Send Byte protocol of the I2C serial interface. System backplanes that do not ground the BD_SEL# signal will instead have circuitry that detects when BD_SEL# has made contact with the plug-in board. The backplane logic can then control the power up process by pulling BD_SEL# low. Figure 4 illustrates the power up sequence. The mating of BD_SEL# is represented by the high to low transition of the BD_SEL# signal. Power-Up Sequence Two external N-channel power MOSFETs isolate the 3.3V and 5V power paths, while two internal MOS switches isolate the 12V and -12V power paths. (See front page Application Circuit). Sense resistors R1 and R2 provide current limit and fault detection for the 3VIN and 5VIN supplies, while R5 and C1 provide current control loop compensation. Current fault detection for the 12V and -12V supplies is done internally.
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A high to low transition on BD_SEL# causes the voltages on the TIMER, GATE, 3VOUT, 5VOUT, 12VOUT and VEEOUT pins to begin ramping (see Figure 4). The TIMER pin capacitance is charged by an 11.5A current source while the GATE capacitance is charged by a 65A current source. Concurrently, an internal charge pump turns on the gates of the internal power switches that isolate the 12V and -12V supplies. All faults are ignored during the time that the voltage at the TIMER pin remains below 5.5V. In order to avoid faults due to the charging of the bulk output capacitors, all output voltages must settle before the TIMER pin reaches 5.5V. See TIMER section for more details. The 5VOUT and 3VOUT supply outputs will ramp up according to the slowest of the following slew rates:
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ILIMIT (5 V)- ILOAD(5 V) dV 65A = , or = , C LOAD(5 VOUT ) dt C1 or =
TIMER 10V/DIV
(1a ) (1b)
ILIMIT (3 V)- ILOAD(3 V) C LOAD(3 VOUT )
GATE 10V/DIV 12VOUT 10V/DIV 5VOUT 10V/DIV 3VOUT 10V/DIV VEEOUT 10V/DIV BD_SEL# 5V/DIV
LCL_PCI_RST# 5V/DIV
HEALTHY# 5V/DIV 10ms/DIV
4240 F04
Figure 4. Normal Power-Up Sequence
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APPLICATIO S I FOR ATIO
Note that capacitor C1 performs dual functions. In addition to controlling the ramp up rates of the 5V and 3.3V outputs, it also compensates the current limit loop. Current limit faults are ignored while the TIMER voltage is less than 5.5V. Once all four supplies are within tolerance, the PWRGD pin (HEALTHY#) will be pulled low and LOCAL_PCI_RESET# (RESETOUT) is free to follow PCI_RST#. Bit 3 of the I2C command latch powers up low, thus not asserting LOCAL_PCI_RST#. Power-Down Sequence When either BD_SEL# (OFF/ON) or Bit 2 of the command latch (C2) is set high, a power-down sequence begins (Figure 5). The TIMER pin is immediately pulled low. The GATE pin (Pin 19) is pulled down by a 200A current source to prevent the load currents on the 3.3V and 5V supplies from going to zero instantaneously and glitching the power
TIMER 10V/DIV
GATE 10V/DIV 12VOUT 10V/DIV 5VOUT 10V/DIV 3VOUT 10V/DIV VEEOUT 10V/DIV BD_SEL# 5V/DIV
LCL_PCI_RST# 5V/DIV
HEALTHY# 5V/DIV 10ms/DIV
4240 F05
Figure 5. Normal Power-Down Sequence
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supply voltages. Internal switches are connected to each of the output supply voltage pins to discharge the output bulk capacitors to ground. When any one of the output voltages drops below its PWRGD threshold, the HEALTHY# signal pulls high, LOCAL_PCI_RST# (RESETOUT) is asserted low, and the external status LED turns on. Once the power-down sequence is complete the status LED will light up and the CPCI card may be removed from the slot. During extraction, the precharge circuit will continue to bias the bus I/O pins at 1V until the long connector pin connections are broken. Early Power Early Power usage is restricted by the CompactPCI (CPCI) specification. It is intended to power up the precharge circuit and I/O cells. The CPCI specification allows any of the long power pins (5V, 3.3V, V(I/O)) to be used for Early Power. Since Early Power is not isolated, a resistor should be placed in series with each CPCI connector pin. Note that if any Early Power pin is shorted on the inserted card, the current limiting resistor will dissipate the power. In order to maximize the DC current available from the 5V supply, all eight 5V connector pins should be tied together on the inserted card. The same applies to the ten 3.3V CPCI connector pins. Early Power should then be drawn from either or both of the two V(I/O) long pins. If either or both of 5V and 3.3V is used for Early Power, then the 5V and 3.3V sense resistor values must be chosen such that the 1A/pin CPCI rule is not violated. Connecting VEEIN To lessen the likelihood of faulting on power up, the VEEOUT output pin should be bypassed with a capacitor that is only as large as necessary. A value of 10F to 47F is recommended. If a large value bypass capacitor is used (e.g. 100F) on VEEOUT, current limit faults may occur during power-up or during recovery from power failures.
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LTC4240
APPLICATIO S I FOR ATIO
Timer
During a power-up sequence, an 11.5A current source is connected to the TIMER pin (Pin 5) and charges up the external TIMER pin capacitor. Current limit faults are ignored until the TIMER voltage ramps to 5.5V. This feature allows the LTC4240 to power-up CPCI boards with widely varying capacitive loads on the back end supplies. The power-up time for either of the two outputs under current limit conditions is given by the slower of:
tON (XVOUT ) = 2 * tON (GATE) = C LOAD(XVOUT) * XVOUT ILIMIT (XVOUT) - ILOAD(XVOUT) or (2a ) (2b)
C1(XVOUT + VTH ) 65A
Where XVOUT = 5VOUT or 3VOUT. The timer period should be set longer than the maximum supply turn-on time but short enough to not exceed the maximum safe operating area of the pass transistor during a short-circuit. VTH is the threshold voltage of the external power FET (2V - 3V). The timer period will be:
tTIMER =
C TIMER * 5.5V 11.5A
The TIMER pin is immediately pulled low when either OFF/ON (Pin 28) or Bit 2 of command latch (C2) goes high. The TIMER pin also functions as a temporary auxiliary supply for 12VIN. In the event of a large (greater than 1V) glitch on 12VIN, the energy stored on the timer capacitor is used as substitute 12VIN power. This improves the glitch immunity of the LTC4240. Thermal Shutdown The internal switches for the 12V and -12V supplies are protected by current limit and thermal shutdown circuits. When the temperature of the die reaches 150C, all four
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switches will be latched off and the FAULT pin (Pin 7) will be pulled low. Since there is no automatic retry, power will have to be cycled with the OFF/ON pin or the I2C command latch. Short-Circuit Protection In order to lower power dissipation in the pass transistors and to mitigate voltage spikes on the supplies during short-circuit conditions, the current limit on each supply is designed to be a function of the output voltage. As the output voltage drops, the current limit decreases. Unlike a traditional circuit breaker function where huge currents can flow before the breaker trips, the current foldback feature lowers short-circuit current by at least 50% when powering up into a short. If any supply is in current limit after the TIMER pin voltage has ramped to 5.5V, then all four pass transistors will be immediately turned off and FAULT will be asserted low (Figure 6).
TIMER 5V/DIV
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(3)
GATE 5V/DIV 12VOUT 10V/DIV 5VOUT 10V/DIV 3VOUT 10V/DIV VEEOUT 10V/DIV BD_SEL# 5V/DIV
FAULT 5V/DIV
10ms/DIV
4240 F06
Figure 6. Power-Up into a Short on 3.3V Output
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LTC4240
APPLICATIO S I FOR ATIO
Once the TIMER voltage has reached 5.5V, all of the supplies will be latched off if any supply enters current limit for at least 35s. The 35s delay prevents quick current spikes--for example, from a fan turning on-- from causing false trips of the circuit breaker. During normal operation, the 5V and 3.3V supplies are protected from overcurrent and short-circuit conditions by dual-level circuit breakers. In the event that either supply current exceeds the nominal limit, an internal timer is started. If the supply is still overcurrent after 35s, the circuit breaker trips and all the supplies are turned off (Figure 7). If a short-circuit occurs on 5VOUT or 3VOUT and the supply current exceeds three times the set limit, an analog loop will limit the current to 3 times the value set by RSENSE and 55mV. If the short persists for more than 35s, the LTC4240 latches off (Figure 8). It will stay in the latched off state until it is reset using the OFF/ON pin or by using the I2C interface. The LTC4240 can also be reset by cycling any of the power supplies.
5VIN-5VSENSE 100mV/DIV
GATE 5V/DIV
FAULT 5V/DIV
20s/DIV
4240 F07
Figure 7. Overcurrent Fault on 5V
5VIN-5VSENSE 100mV/DIV
GATE 5V/DIV
FAULT 5V/DIV
20s/DIV
4240 F08
Figure 8. Short-Circuit Fault on 5V
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The current limit and the foldback current level for the 5V and 3.3V outputs are both a function of the external sense resistor (R1 for 3VOUT and R2 for 5VOUT, see front page). A sense resistor is connected between 5VIN (Pin 21) and 5VSENSE (Pin 20) for the 5V supply. For the 3.3V supply, a sense resistor is connected between 3VIN (Pin 22) and 3VSENSE (Pin 23). The current limit and the current foldback current level are given by Equations 4 and 5:
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ILIMIT (XVOUT) =
55mV RSENSE(XVOUT) 11mV RSENSE(XVOUT)
(4) (5)
IFOLDBACK(XVOUT) =
where XVOUT = 5VOUT or 3VOUT. Equation 4 is the current limit for XVOUT XVIN. Equation 5 shows the ILIMIT for shorted outputs. Both equations assume voltage on TIMER pin is greater than 5.5V. XVOUT = 3VOUT or 5VOUT. Note that since there are only 8 pins connecting 5VIN, RSENSE 0.007 for 5VIN. The current limit for the internal 12V switch is set at -1200mA folding back to -350mA and the -12V switch at 500mA folding back to 250mA. Selecting RSENSE An equivalent circuit for the 5V and 3.3V circuit breakers is shown in Figure 9. The sense resistor and the circuit breaker threshold voltage determine the fault current that turns off the external FETs. Sense resistors with a 1% tolerance are recommended. Due to part to part and temperature variations for both the sense resistor value and the circuit breaker threshold voltage, the actual current limit threshold will exhibit some variation. To calculate the smallest value of current that will trip the fault comparator, use the largest value of the sense resistor and the smallest value of the threshold voltage. A 0.005 1% sense resistor (on the 3.3V supply, for example) with typical temperature coefficients would increase to approximately 0.0051 (nominal value multiplied by the 1% tolerance and the TC at 70C). Since the minimum value of the threshold voltage is 50mV, this implies a current limit of 9.8A. To arrive at the largest value of the current limit that will turn off the external FETs, the nominal value of the
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LTC4240
APPLICATIO S I FOR ATIO
sense resistor drops to 0.0049 and the largest value of threshold voltage increases to 60mV. This results in a trip current of 12.2A.
ILOAD(MAX) 5VIN 21 5VIN 20 5VSENSE VCB LTC4240* RSENSE
+ - -
+
VCB(MAX) = 60mV VCB(NOM) = 55mV VCB(MIN) = 50mV
*ADDITIONAL DETAILS OMITTED FOR CLARITY
4240 F09
Figure 9. Circuit Breaker Equivalent Circuit for Calculating RSENSE
Plug-in board designers are thus limited to using less than 9.8A when a nominal 0.005 resistor is used. Using more than 9.8A runs the risk of turning off the external FET. Since the CompactPCI specification allows a maximum 1A/pin, at least 10 pins must be used to supply 9.8A. This implies that only the 3.3V supply can use a 0.005 resistor, since the 5V supply has a maximum of 8 pins available. To adhere to the 1A/pin specification, the 5V sense resistor should be larger than the 3.3V sense resistor. Typical applications show a nominal 0.007 resistor, which results in a 7.04A maximum deliverable current to the plug-in board loads. The 7.04A current implies at least 7 pins on the 5V connector. Note that the thermal considerations of the external FET will also place limitations on the maximum allowable current. 5V and 3.3V External FET Selection The LTC4240 uses external power FETs to limit and modulate the current delivered by the 3.3V and 5V supplies. There are several parameters to consider when selecting the FET: 1. On resistance. 2. Gate and drain breakdown voltage. 3. Steady state and transient power dissipation.
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On Resistance The CompactPCI specification limits the total IR drop of the FET plus the IR drop of the sense resistor to 100mV. For a nominal sense resistor of 0.005, if the user limits the 3.3V supply load current to 8.7A, then the maximum FET resistance should be less than 0.0063. Similarly, for a 6.2A load current on the 5V supply and a 0.007 sense resistor, the maximum 5V FET resistance should be 0.0088. Note that above values of FET resistance are worst case over temperature (on the FET's datasheet, find the resistance vs temperature curve and de-rate the room temperature maximum value). Breakdown Voltage The maximum DC voltage that can appear across the drain/source of the external power FET is 5V +10%. During transient events and hot swap conditions, parasitic inductances could cause ringing up to 3 times the supply voltage. The use of voltage transient suppressors at the 5V and 3.3V inputs can limit these voltage swings to less than 10V (see front page schematic). Similarly, the largest DC voltage that is likely to appear across the gate is 12V +10%. Voltage suppressors on the 12VIN node will also limit the transient spikes on that node. Additionally, the total capacitance on the GATE node will serve to filter fast voltage noise spikes. FETs with a minimum rating of 20V on both the drain/source and the gate/source are recommended. Steady State Power Dissipation For a user selected maximum load current of 8.7A on the 3.3V power supply and a 0.0063 maximum FET resistance, the DC power dissipation is: (IMAX)2(RDSON,MAX) = (8.7)(8.7)(0.0063) = 0.477W This is within the SOA limits of most power FETs.
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LTC4240
APPLICATIO S I FOR ATIO
Transient Power Dissipation
There are certain transient events that can significantly increase the power dissipated by the external FET. If the LTC4240 5V supply (at 5V + 10%) powers up into a 1.5V short (potentially manifested as a short to two diodes in series), then the FET can potentially have 4V across it with 8.8A flowing. This implies a power dissipation of 35.1W. The amount of time the FET will dissipate 35.1W will depend on the relative values of the TIMER and GATE capacitances. For the values specified on the front page application circuit, the GATE pin will ramp high significantly faster than the TIMER pin, hence transient power dissipation will be set by the TIMER pin capacitance. The dissipated 35.1W, the ramp time of the TIMER pin (50ms will be used for this example), and the FET thermal resistance will determine the internal junction temperature of the FET. Most FETs will specify a maximum internal junction temperature of 150C. The FET datasheets should have a transient thermal impedance graph. This graph has a family of curves listing the FET transient thermal impedance as a function of duty cycle. The duty cycle refers to what percentage of the time the FET is in the short circuit condition. If we choose the Si7880DP FET and assume that the board on which the FET is placed has minimal heat sinking capability, and further assume that the user will turn on the board every 2.5 seconds (0.02 duty cycle: 50ms on, 2450ms off), then by looking at the junction-toambient curve we note that with a 70C ambient temperature, the Si7880DP internal junction temperature will be 172C. This is above the absolute maximum rating of the FET, and although operating at this temperature will not damage the FET immediately, it does affect its long term reliability. Conversely, if we assume that there is a perfect heat sink for the Si7880DP package, then we would use the junction-to-case curve and calculate a value of 117C with a 70C ambient temperature. The Si7880DP comes in a thermally enhanced package whose drain lead is a large piece of metal that can conduct heat away from the internal junction of the FET. To achieve best performance, the drain of the Si7880DP should be connected to a piece of copper (as large as possible) on the board. Note that if the output is shorted to ground, the current foldback feature will cut the power dissipation by at least a factor of two.
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When the LTC4240 is turned on and the large 5VOUT output capacitor (2000F or more) is charged, it is possible that the 5V FET will dissipate as much as the 35.1W described above. If there is no DC load at 5VOUT, then 8.8A will charge the 2000F in less than 2ms, which should not pose any thermal problems for the Si7880DP. If the DC load at 5VOUT approaches the current limit, then the above analysis should be used to calculate the internal junction temperature of the FET. Output Voltage Monitor The DC level of all four supply outputs is monitored by the power good circuitry. When any of the four supply outputs falls below its specified level (see DC electrical specifications) for longer than 10s, the PWRGD (HEALTHY#) open drain pin will be deasserted and the LOCAL_PCI_RST# signal will be asserted low. This does not generate a fault condition. The LOCAL_PCI_RST# signal (RESETOUT pin) is derived from the HEALTHY# (PWRGD pin), PCI_RST# (RESETIN pin), and Bit 3 of the command latch (see Table 5).
Table 5. LOCAL_PCI_RST# Truth Table
PCI_RST# LO X X HI HEALTHY# X HI X LO Bit 3 (C3 ) Command Latch X X HI LO LOCAL_PCI_RST# LO LO LO HI
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Precharge The PRECHARGE input and DRIVE output pins are used to generate the 1V precharge voltage that biases the bus I/O connector pins during board insertion and extraction (Figure 10). The LTC4240 is capable of generating precharge voltages other than 1V. Figure 11 shows a circuit that can be used in applications requiring a precharge voltage less than 1V. The circuit in Figure 12 can be used for applications that need precharge voltages greater than 1V. Table 6 lists suggested resistor values for R11A and R11B vs precharge voltage for the application circuits shown in Figures 11 and 12.
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LTC4240
APPLICATIO S I FOR ATIO
VPRECHARGE 1.5V 1.4V 1.3V 1.2V 1.1V 1V R11A 18 18 18 18 18 18 R11B 9.09 7.15 5.36 3.65 1.78 0 VPRECHARGE 0.9V 0.8V 0.7V 0.6V 0.5V R11A 16.2 14.7 12.1 11 9.09
Table 6. R1 and R2 Resistor Values vs Precharge Voltages
R11B 1.78 3.65 5.11 7.15 9.09
CompactPCI BACKPLANE CONNECTOR (MALE) MEDIUM 5V LONG 5V 3.3V LONG 3.3V
CompactPCI BACKPLANE CONNECTOR (FEMALE)
5VIN
R22 2.74 3VIN R21 1.74 22
GROUND RI01 10, 5% I/O PIN 1
*** ***
DATA BUS RI0128 10, 5%
I/O PIN 128 *ADDITIONAL DETAILS OMITTED FOR CLARITY
Figure 10. Precharge Application Circuit
LTC4240* GND 10 C3 4.7nF PRECHARGE 18 R9 24, 5% DRIVE 17
R8 1k, 5% R7 12, 5%
R11A R11B PRECHARGE OUT R11A * 1V VPRECHARGE = R11A + R11B
Q3 MMBT2222A *ADDITIONAL DETAILS OMITTED FOR CLARITY
Figure 11. Precharge Voltage Less Than 1V
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Precharge resistors are used to connect the 1V bias voltage to the CompactPCI connector I/O lines. This allows live insertion of the I/O lines with minimal disturbance. Figure 13 shows the precharge application circuit for 5V signaling environments. The precharge resistor requirements are more stringent for 3.3V and Universal Hot Swap signaling. If the total leakage current on the I/O line is less
21 5VIN LTC4240* 3VIN GND 10 R11 18, 5% PRECHARGE OUT 1V 20% IOUT = 55mA PRECHARGE 18 C3 4.7nF RPRE1 10k 5% R9 24, 5% DRIVE 17 R8 1k, 5% 3VIN Q3 R7 MMBT2222A RPRE128 12, 5% 10k 5% I/O
*** ***
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UP TO 128 I/O LINES
I/O
PCI BRIDGE (21154)
4240 F10
LTC4240* GND PRECHARGE 10 18 R9 C3 24, 5% 4.7nF R11A R11B DRIVE 17
R8 1k, 5% R7 12, 5%
3VIN
4240 F11
Q3 MMBT2222A PRECHARGE OUT *ADDITIONAL DETAILS VPRECHARGE = R11A + R11B * 1V OMITTED FOR CLARITY R11A
3VIN
4240 F12
Figure 12. Precharge Voltage Greater Than 1V
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APPLICATIO S I FOR ATIO
than 2A, then a 50K resistor can be connected directly from the 1V bias voltage to the I/O line. However, many ICs connected to the I/O lines can have leakage currents up to 10A. For these applications, a 10k resistor is used but must be disconnected when the board has been seated as determined by the state of the BD_SEL# signal. Figure 14 shows a precharge circuit that uses a bus switch to
CompactPCI BACKPLANE CONNECTOR (MALE) MEDIUM 5V LONG 5V BD_SEL# CompactPCI BACKPLANE CONNECTOR (FEMALE) R22 2.74
5VIN
Z4
R18 1k, 5% 28 OFF/ON R17 GND 1.2k 5% LONG 5V RI01 10 5%
GROUND
I/O PIN 1 DATA BUS RI0128 10 5%
I/O PIN 128 Z4: 1PMT5.0AT3 *ADDITIONAL DETAILS OMITTED FOR CLARITY
Figure 13.Precharge Application Circuit for 5V Signaling Systems
CompactPCI BACKPLANE CONNECTOR (MALE) MEDIUM 5V LONG 5V BD_SEL# CompactPCI BACKPLANE CONNECTOR (FEMALE) 5VIN R22 2.74 R17 1.2k 5% 21 5V IN R18 1k, 5% 28 OFF/ON GND 10 R11 18, 5% GROUND R26 51.1k, 5% LONG 5V 100 Q4 MMBT3906 0.1F OE RI01 10 5% RI0128 10 5% LTC4240*
Z4
I/O PIN 1
DATA BUS
I/O PIN 128 Z4: 1PMT5.0AT3 *ADDITIONAL DETAILS OMITTED FOR CLARITY
Figure 14. Precharge Bus Switch Application Circuit for 3.3V and Universal Hot Swap Boards
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connect the individual 10k precharge resistors to the LTC4240 1V PRECHARGE pin. The electrical connection is made (bus switches close) when the voltage on the BD_SEL# pin of the plug-in card is above 4.4V, which occurs just after the long pins have made contact. The bus switches are subsequently electrically disconnected when the board connector makes contact with the BD_SEL# pin (bus switch OE pin is pulled high by Q4).
21 5V IN LTC4240* PRECHARGE 18 C3, 4.7nF RPRE128 10k 5% R9 24 3VIN DRIVE 17 R8 1k, 5% R11 18, 5% RPRE1 10k 5% Q3 PRECHARGE OUT MMBT2222A R7 1V 10% 12, 5% IOUT = 55mA I/O UP TO 128 I/O LINES I/O PCI BRIDGE CHIP
4240 F13
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***
***
***
***
PRECHARGE 18 R9 24 C3, 4.7nF
DRIVE 17 R8 1k, 5% 3VIN
R27 75k 5%
IN VDD BUS SWITCH OUT OUT RPRE1 RPRE128 10k 10k 5% 5%
Q3 R7 MMBT2222A 12, 5% PRECHARGE OUT 1V 10% IOUT = 55mA
I/O PCI BRIDGE CHIP
4240 F14
***
***
UP TO 128 I/O LINES
I/O
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LTC4240
APPLICATIO S I FOR ATIO
The assumption by the CompactPCI specification is that there is a diode to 3.3V on the circuit that is driving the BD_SEL# pin. The 1.2k resistor pull up to 5VIN on the plugin card will thus be clamped by the diode to 3.3V. If the BD_SEL# pin is being driven high, the actual voltage on the pin will be approximately 3.9V. This is still above the high TTL threshold of the LTC4240 OFF/ON pin, but low enough for Q4 to disable the bus switches and thus remove the 10k resistors from the I/O lines. Note that BD_SEL# is ordinarily connected to V(I/O), which in turn is allowed to be driven by either 3.3V or 5V. For applications such as shown in Figure 14, the pull up on BD_SEL# is restricted to the long 5V pins. A bus switch with no internal diode to VDD is preferred. Since the power to the bus switch is derived from one of the unswitched power planes, a 100 resistor plus a 0.1F bypass capacitor should be placed in series with its power supply. When the plug-in card is removed from the connector, the BD_SEL# connection is broken first, and the BD_SEL# voltage pulls up to 5V. This causes Q4 to turn off, which reenables the bus switch, and the precharge resistors are again connected to the LTC4240 PRECHARGE pin for the remainder of the board extraction process. The LTC4240 BE pin can alternatively be used to drive the enable input of the bus switch. The BE signal would then keep the I/O lines precharged until all supplies reached power good status. The resistor in series with the PRECHARGE pin protects the internal circuitry from large voltage transients during live insertion. PRSNT1#, PRSNT2# PRSNT1# and PRSNT2# are PCI signals that convey the plug-in board's power consumption information. These pins should either be shorted to ground or be connected to Early Power with a 10k resistor. The voltage levels (TTL) at the PRSNT#1, 2 pins can be read using the I2C 2-wire interface.
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PRSNT1# Open Ground 10k Pull-Up Ground PRSNT2# Open 10k Pull-Up Ground Ground Expansion Configuration No plug in board present Plug-in board present, maximum power consumption Plug-in board present, nominal power consumption Plug-in board present, minimum power consumption
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Other CompactPCI Applications If no 3.3V supply input is required, Figure 15 illustrates how the LTC4240 should be configured. For applications where the BD_SEL# connector pin is grounded on the backplane, the circuit in Figure 16 allows the LTC4240 to be reset simply by pressing a pushbutton switch on the CPCI plug-in board. This arrangement allows for manual resetting of the LTC4240's circuit breakers. Input Transient Protection Hot-plugging a board into a backplane generates inrush currents from the backplane power supplies. This is due to the charging of the plug-in board bulk capacitance. To reduce this transient current to a safe level, the CPCI Hot Swap specification restricts the amount of unswitched capacitance used on the input side of the plug-in board. Each pin connected to the CPCI female connector on the plug-in board is allowed at most 0.01F/pin. Bulk capacitors are only allowed on the switched output side of the LTC4240 (5VOUT, 3VOUT, 12VOUT, VEEOUT). Some bulk capacitance is allowed on the Early Power planes, but only because a current limiting resistor is assumed to separate the connector from the bulk capacitor. Circuits normally placed on the unswitched Early Power (PCI Bridge, for example) need to have a current limiting resistor.
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APPLICATIO S I FOR ATIO
Disallowing bulk capacitors on the input power pins mitigates the inrush current during hot plug. However, it also tends to create a resonant circuit formed by the inductance of the backplane power supply trace and the parasitic capacitance of the plug-in board (mainly due to the large power FET). Upon board insertion, the ringing of this circuit will exhibit peak overshoot as high as 2.5 times the steady state voltage (>30V for 12V). There are two methods for abating the effects of these high voltage transients: using zener clamps, and using snubber
CompactPCI CompactPCI BACKPLANE BACKPLANE CONNECTOR CONNECTOR (FEMALE) (MALE) MEDIUM 5V LONG 5V
5VIN Z4 D1 D2
R22 2.74
GND D1, D2: BAV99 Z4: 1PMT5.0AT3
Figure 15. 5V Supply Only Application Circuit
CompactPCI CompactPCI BACKPLANE BACKPLANE CONNECTOR CONNECTOR (FEMALE) PUSHBUTTON (MALE) SWITICH BD_SEL# 100 V(I/O)
GND
*ADDITIONAL DETAILS OMITTED FOR CLARITY
Figure 16. BD_SEL# Pushbutton Toggle Switch
R2 0.007 MEDIUM 5V R22, 2.74 LONG 5V MEDIUM 3.3V R21, 1.74 LONG 3.3V R3 10 R4 10 R5 1k C1 0.047F R1 0.005 Q1 Si7880DP Q2 Si7880DP
R23 2.7 Z3 C7 0.1F
22 3VIN
3VSENSE GATE
Z3, Z4: 1PMT5.0AT3 *ADDITIONAL DETAILS OMITTED FOR CLARITY
Figure 17. Place Transient Protection Device Close to the LTC4240
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networks. Snubbers are RC networks whose time constants are large enough to damp the inductance of the parasitic resonant circuit. The snubber capacitor should be 10X to 100X the value of the plug-in board parasitic capacitance. The value of the series snubber resistor should be large enough to damp the resulting R-L-C circuit and is typically between 1 and 50. These protection networks should be mounted very close to the LTC4240 in order to minimize parasitic inductance. This is shown in Figure 17 for the 3.3V and 5V supplies.
R2 0.007 Q2 Si7880DP 5VOUT CL(5VOUT) R4 10 C1 R5 0.047F 1k 22 3VIN 10 GND 23 3VSENSE 21 5VIN 20 19 6 24 5VSENSE GATE LTC4240*
4240 F15
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5VOUT 3VOUT
*ADDITIONAL DETAILS OMITTED FOR CLARITY
1.2k 1k 28
OFF/ON LTC4240*
10
GND
4240 F16
5VOUT AT 5A 3VOUT AT 7.6A
23
19
24 3VOUT GND 5VIN
21
20 5VSENSE
6 5VOUT 2.7 Z4 0.1F
LTC4240*
10
1644 F17
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APPLICATIO S I FOR ATIO
Note (see front page schematic) that the 12V and -12V show 0.01F snubber capacitors. This is consistent with the CPCI specification since we also recommend a 10 snubber resistor. The 12VIN pin is the most sensitive to high energy large voltage transients. A transient voltage suppressor with a breakdown voltage between 13.2V and 15V is advisable. The TVS should also be able to dissipate at least 150W. The SMAJ12CA can be used for both 12VIN and VEEIN. Place the TVS close to the LTC4240. See front page schematic.
CURRENT FLOW TO LOAD POWER MOSFET CURRENT FLOW TO LOAD
SENSE RESISTOR D
G S S S W 5VOUT 5V
5VIN 5V
D W D D
TRACK WIDTH W: 0.03" PER AMPERE ON 1OZ Cu FOIL
R4 GATE R5 C1
28
27
26
25
24
23
22
21
20
19
18
17
16
15
LTC4240CGN* SIMILAR LAYOUT FOR 3.3V RAIL NOT SHOWN
10
11
12
13
CTIMER
CURRENT FLOW TO SOURCE
14
1
2
3
4
5
6
7
8
9
GND
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*ADDITIONAL DETAILS OMITTED FOR CLARITY. DRAWING IS NOT TO SCALE!
Figure 18. Recommended Layout for Power MOSFET, Sense Resistor and GATE Components for the 5V Rail. Similar Layout for 3.3V Rail Not Shown
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PCB Layout Considerations For proper operation of the LTC4240's circuit breaker function, a 4-wire Kelvin connection to the sense resistors is highly recommended. A recommended PCB layout for the sense resistor, the power MOSFET, and the GATE drive components around the LTC4240 is illustrated in Figure 18. The drawing is not to scale and is only intended to show the low resistance, external high current path. In hot swap applications where load currents can reach 10A, narrow PCB tracks exhibit more resistance than wider tracks and operate at more elevated temperatures. Since the sheet resistance of 1 ounce copper is approximately 0.5m/square, track resistances add up quickly in highcurrent applications. Thus, to keep PCB track resistance and temperature rise to a minimum, the suggested trace width in these applications for 1 ounce copper is 0.03" for each ampere of DC current. In order to help dissipate the heat generated by the power MOSFET, the copper trace connected to the drain should be made as large as possible. In the majority of applications, it will be necessary to use plated-through vias to make circuit connections from component layers to power and ground layers internal to the PC board. For 1 ounce copper plating, a general rule is 1A of DC current per via, making sure the via is properly dimensioned so that solder completely fills any void. For other plating thicknesses, check with your PCB fabrication facility. Power MOSFET and Sense Resistor Selection
4240 F18
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VIA/PATH TO GND
VIA TO GND PLANE
GND
Table 7 lists some current MOSFET transistors that are available. Table 8 lists some current sense resistors that can be used with the LTC4240's circuit breakers. Table 9 lists supplier web site addresses for discrete components mentioned throughout the LTC4240 data sheet. High current applications should select a MOSFET with very low on-resistance and good transient thermal characteristics.
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APPLICATIO S I FOR ATIO
CURRENT LEVEL (A) 0 to 2 2 to 5 5 to 10 5 to 10 5 to 10 PART NUMBER MMDF3N02HD MMSF5N02HD MTB50N06V IRF7457 Si7880DP
Table 7. N-Channel Power MOSFET Selection Guide
DESCRIPTION Dual N-Channel SO-8 RDS(ON) = 0.1 Single N-Channel SO-8 RDS(ON) = 0.025 Single N-Channel DD-Pak RDS(ON) = 0.028 Single N-Channel SO-8 RDS(ON) = 0.007 Single N-Channel PowerPAKTM RDS(ON) = 0.003 MANUFACTURER ON Semiconductor ON Semiconductor ON Semiconductor International Rectifier Vishay-Siliconix
Table 8. Sense Resistor Selection Guide
CURRENT LIMIT VALUE 1A 2A 5A 7.9A 11A PART NUMBER LR120601R055F WSL1206R055 LR120601R028F WSL1206R028 LR120601R011F WSL2010R011 WSL2512R007 WSL2512R005 DESCRIPTION 0.055, 0.5W, 1% Resistor 0.028, 0.5W, 1% Resistor 0.011, 0.5W, 1% Resistor 0.007, 1W, 1% Resistor 0.005, 1W, 1% Resistor MANUFACTURER IRC-TT Vishay-Dale IRC-TT Vishay-Dale IRC-TT Vishay-Dale Vishay-Dale Vishay-Dale
PowerPAK is a trademark of Vishay-Siliconix
Table 9. Manufacturers' Web Site
MANUFACTURER International Rectifier ON Semiconductor IRC-TT Vishay-Dale Vishay-Siliconix Diodes, Inc. WEB SITE www.irf.com www.onsemi.com www.irctt.com www.vishay.com www.vishay.com www.diodes.com
Information furnished by Linear Technology Corporation is believed to be accurate and reliable. However, no responsibility is assumed for its use. Linear Technology Corporation makes no representation that the interconnection of its circuits as described herein will not infringe on existing patent rights.
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LTC4240
PACKAGE DESCRIPTIO
.254 MIN
.0165 .0015 RECOMMENDED SOLDER PAD LAYOUT
.0075 - .0098 (0.191 - 0.249) .016 - .050 (0.406 - 1.270)
NOTE: 1. CONTROLLING DIMENSION: INCHES INCHES 2. DIMENSIONS ARE IN (MILLIMETERS) 3. DRAWING NOT TO SCALE *DIMENSION DOES NOT INCLUDE MOLD FLASH. MOLD FLASH SHALL NOT EXCEED 0.006" (0.152mm) PER SIDE **DIMENSION DOES NOT INCLUDE INTERLEAD FLASH. INTERLEAD FLASH SHALL NOT EXCEED 0.010" (0.254mm) PER SIDE
RELATED PARTS
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4240f LT/TP 0403 2K * PRINTED IN USA
LTC1643AL/LTC1643AL-1/ PCI Bus Hot Swap Controllers LTC1643AH LTC1644 LTC1645 LTC1646 LTC1647 LTC4211 LTC4230 LTC4241 LT4250L/LT4250H LTC4251 LTC4252 LTC4350 CompactPCI Hot Swap Controller 2-Channel Hot Swap Controller CompactPCI Hot Swap Controller for 3.3V and 5V Dual Hot Swap Controller Triple Hot Swap Controller with Multifunction Current Control PCI Hot Swap Controller with 3.3V Auxiliary -48 Hot Swap Controllers in SO-8 -48 Hot Swap Controller in SOT-23 -48 Hot Swap Controller in MSOP Hot Swappable Load Share Controller
Single Hot Swap Controller with Multifunction Current Control 2.5V to 16.5V, Dual Level Circuit Breaker, No Gate Capacitor
28
Linear Technology Corporation
1630 McCarthy Blvd., Milpitas, CA 95035-7417
(408) 432-1900 q FAX: (408) 434-0507
q
U
GN Package 28-Lead Plastic SSOP (Narrow .150 Inch)
(Reference LTC DWG # 05-08-1641)
.045 .005 .386 - .393* (9.804 - 9.982) 28 27 26 25 24 23 22 21 20 19 18 17 1615 .033 (0.838) REF .150 - .165 .229 - .244 (5.817 - 6.198) .150 - .157** (3.810 - 3.988) .0250 TYP 1 .053 - .069 (1.351 - 1.748) 23 4 56 7 8 9 10 11 12 13 14 .004 - .009 (0.102 - 0.249) .015 .004 x 45 (0.38 0.10) 0 - 8 TYP .008 - .012 (0.203 - 0.305) .0250 (0.635) BSC
GN28 (SSOP) 0502
www.linear.com
(c) LINEAR TECHNOLOGY CORPORATION 2003

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